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| TNY174-180 (R) TinySwitch-LT Family Energy Efficient, Offline Switcher with Enhanced Flexibility and Extended Power Range Product Highlights Lowest System Cost with Enhanced Flexibility * 650 V rating optimized for non-active PFC applications * Simple ON/OFF control, no loop compensation needed * Selectable current limit through BP/M capacitor value - Higher current limit extends peak power or, in open frame applications, maximum continuous power www..com - Lower current limit improves efficiency in enclosed adapters/chargers - Allows optimum TinySwitch-LT choice by swapping devices with no other circuit redesign * Tight I2f parameter tolerance reduces system cost - Maximizes MOSFET and magnetics power delivery - Minimizes max overload power, reducing cost of transformer, primary clamp & secondary components * ON-time extension - extends low line regulation range/ hold-up time to reduce input bulk capacitance * Self-biased: no bias winding or bias components * Frequency jittering reduces EMI filter costs * Pin-out simplifies heatsinking to the PCB * SOURCE pins are electrically quiet for low EMI Enhanced Safety and Reliability Features * Accurate hysteretic thermal shutdown protection with automatic recovery eliminates need for manual reset * Auto-restart delivers <3% of maximum power in short circuit and open loop fault conditions * Output overvoltage shutdown with optional Zener * Very low component count enhances reliability and enables single-sided printed circuit board layout * High bandwidth provides fast turn on with no overshoot and excellent transient load response * Extended creepage between DRAIN and all other pins improves field reliability EcoSmart - Extremely Energy Efficient * Easily meets all global energy efficiency regulations * No-load <150 mW at 265 VAC without bias winding, <50 mW with bias winding * ON/OFF control provides constant efficiency down to very light loads - ideal for mandatory CEC regulations Applications * Chargers/adapters for cell/cordless phones, PDAs, digital cameras, MP3/portable audio, shavers, etc. * DVD/PVR and other low power set top decoders * Supplies for appliances, industrial systems, metering, etc. (R) AC Input + DC Output D EN BP/M S TinySwitch-LT PI-4770-073107 Figure 1. Typical Application. OUTPUT POWER TABLE 230 VAC 15% PRODUCT3 TNY174PN TNY175PN TNY176PN TNY177PN TNY178PN TNY179PN TNY180PN 85-265 VAC Peak or Peak or Adapter1 Open Adapter1 Open Frame2 Frame2 6W 8.5 W 10 W 13 W 16 W 18 W 20 W 11 W 15 W 19 W 23.5 W 28 W 32 W 36.5 W 5W 6W 7W 8W 10 W 12 W 14 W 8.5 W 11.5 W 15 W 18 W 21.5 W 25 W 28.5 W Table 1. Notes: 1. Minimum continuous power in a typical nonventilated enclosed adapter measured at 50 C ambient. Use of an external heatsink will increase power capability 2. Minimum peak power capability in any design or minimum continuous power in an open frame design (see Key Application Considerations). 3. Packages: P: DIP-8C, G: SMD-8C. See Part Ordering Information. Description TinySwitch-LT incorporates a 650 V power MOSFET, oscillator, high voltage switched current source, current limit (user selectable) and thermal shutdown circuitry. The IC family uses an ON/OFF control scheme and offers a design flexible solution with a low system cost and extended power capability. August 2007 TNY174-180 BYPASS/ MULTI-FUNCTION (BP/M) REGULATOR 5.85 V DRAIN (D) 115 A AUTORESTART COUNTER RESET FAULT PRESENT + BYPASS PIN UNDER-VOLTAGE BYPASS CAPACITOR SELECT AND 5.85 V 4.9 V CURRENT LIMIT STATE MACHINE VI LIMIT CURRENT LIMIT COMPARATOR ENABLE + www..com 1.0 V + VT JITTER CLOCK DCMAX OSCILLATOR THERMAL SHUTDOWN ENABLE (EN) 1.0 V S Q R Q OVP LATCH LEADING EDGE BLANKING SOURCE (S) PI-4771-073107 Figure 2. Functional Block Diagram. Pin Functional Description DRAIN (D) Pin: This pin is the power MOSFET drain connection. It provides internal operating current for both startup and steady-state operation. BYPASS/MULTI-FUNCTION (BP/M) Pin: This pin has multiple functions: 1. It is the connection point for an external bypass capacitor for the internally generated 5.85 V supply. 2. It is a mode selector for the current limit value, depending on the value of the capacitance added. Use of a 0.1 F capacitor results in the standard current limit value. Use of a 1 F capacitor results in the current limit being reduced to that of the next smaller device size. Use of a 10 F capacitor results in the current limit being increased to that of the next larger device size for TNY175-180. 3. It provides a shutdown function. When the current into the bypass pin exceeds ISD, the device latches off until the BP/M voltage drops below 4.9 V, during a power down. This can be used to provide an output overvoltage function P Package (DIP-8C) EN BP/M 1 2 8 7 6 S S S S D 4 5 PI-4772-07307 Figure 3. Pin Configuration. with a Zener connected from the BP/M pin to a bias winding supply. ENABLE (EN) Pin: The switching of the power MOSFET is controlled by this pin. MOSFET switching is terminated when a current greater than 2 A 08/07 TNY174-180 a threshold current is drawn from this pin. Switching resumes when the current being pulled from the pin drops to less than a threshold current. A modulation of the threshold current reduces group pulsing. The threshold current is between 75 A and 115 A. SOURCE (S) Pin: This pin is internally connected to the output MOSFET source for high voltage power return and control circuit common. jitter is set to 1 kHz to optimize EMI reduction for both average and quasi-peak emissions. The frequency jitter should be measured with the oscilloscope triggered at the falling edge of the DRAIN waveform. The waveform in Figure 4 illustrates the frequency jitter. Enable Input and Current Limit State Machine The enable input circuit at the EN pin consists of a low impedance source follower output set at 1.2 V. The current through the source follower is limited to 115 A. When the current out of this pin exceeds the threshold current, a low logic level (disable) is generated at the output of the enable circuit, until the current out of this pin is reduced to less than the threshold current. This enable circuit output is sampled at the beginning of each cycle on the rising edge of the clock signal. If high, the power MOSFET is turned on for that cycle (enabled). If low, the power MOSFET remains off (disabled). Since the sampling is done only at the beginning of each cycle, subsequent changes in the EN pin voltage or current during the remainder of the cycle are ignored. The current limit state machine reduces the current limit by discrete amounts at light loads when TinySwitch-LT is likely to switch in the audible frequency range. The lower current limit raises the effective switching frequency above the audio range and reduces the transformer flux density, including the associated audible noise. The state machine monitors the sequence of enable events to determine the load condition and adjusts the current limit level accordingly in discrete amounts. Under most operating conditions (except when close to no-load), the low impedance of the source follower keeps the voltage on the EN pin from going much below 1.2 V in the disabled state. This improves the response time of the optocoupler that is usually connected to this pin. 5.85 V Regulator and 6.4 V Shunt Voltage Clamp The 5.85 V regulator charges the bypass capacitor connected to the BYPASS pin to 5.85 V by drawing a current from the voltage on the DRAIN pin whenever the MOSFET is off. The BYPASS/MULTI-FUNCTION pin is the internal supply voltage node. When the MOSFET is on, the device operates from the energy stored in the bypass capacitor. Extremely low power consumption of the internal circuitry allows TinySwitch-LT to operate continuously from current it takes from the DRAIN pin. A bypass capacitor value of 0.1 F is sufficient for both high frequency decoupling and energy storage. In addition, there is a 6.4 V shunt regulator clamping the BYPASS/MULTI-FUNCTION pin at 6.4 V when current is provided to the BYPASS/MULTI-FUNCTION pin through an external resistor. This facilitates powering of TinySwitch-LT externally through a bias winding to decrease the no-load consumption to well below 50 mW. TinySwitch-LT Functional Description TinySwitch-LT combines a high voltage power MOSFET switch with a power supply controller in one device. Unlike www..com (pulse width modulator) controllers, it uses conventional PWM a simple ON/OFF control to regulate the output voltage. The controller consists of an oscillator, enable circuit (sense and logic), current limit state machine, 5.85 V regulator, BYPASS/ MULTI-FUNCTION pin undervoltage, overvoltage circuit, and current limit selection circuitry, over- temperature protection, current limit circuit, leading edge blanking, and a 700 V power MOSFET. TinySwitch-LT incorporates additional circuitry for auto-restart, adaptive switching cycle on-time extension, and frequency jitter. Figure 2 shows the functional block diagram with the most important features. Oscillator The typical oscillator frequency is internally set to an average of 132 kHz. Two signals are generated from the oscillator: the maximum duty cycle signal (DCMAX) and the clock signal that indicates the beginning of each cycle. The oscillator incorporates circuitry that introduces a small amount of frequency jitter, typically 8 kHz peak-to-peak, to minimize EMI emission. The modulation rate of the frequency PI-2741-041901 600 500 VDRAIN 400 300 200 100 0 136 kHz 128 kHz 0 5 Time (s) 10 Figure 4. Frequency Jitter. A 08/07 3 TNY174-180 BYPASS/MULTI-FUNCTION Pin Undervoltage The BYPASS/MULTI-FUNCTION pin undervoltage circuitry disables the power MOSFET when the BYPASS/MULTIFUNCTION pin voltage drops below 4.9 V in steady state operation. Once the BYPASS/MULTI-FUNCTION pin voltage drops below 4.9 V in steady state operation, it must rise back to 5.85 V to enable (turn-on) the power MOSFET. Over Temperature Protection The thermal shutdown circuitry senses the die temperature. The threshold is typically set at 142 C with 75 C hysteresis. When the die temperature rises above this threshold the power MOSFET is disabled and remains disabled until the die temperature falls by 75 C, at which point it is re-enabled. A large hysteresis of 75 C (typical) is provided to prevent overheating of the PC board due to a continuous fault condition. www..com Current Limit The current limit circuit senses the current in the power MOSFET. When this current exceeds the internal threshold (ILIMIT), the power MOSFET is turned off for the remainder of that cycle. The current limit state machine reduces the current limit threshold by discrete amounts under medium and light loads. The leading edge blanking circuit inhibits the current limit comparator for a short time (tLEB) after the power MOSFET is turned on. This leading edge blanking time has been set so that current spikes caused by capacitance and secondary-side rectifier reverse recovery time will not cause premature termination of the switching pulse. Auto-Restart In the event of a fault condition such as output overload, output short circuit, or an open loop condition, TinySwitch-LT enters into auto-restart operation. An internal counter clocked by the oscillator is reset every time the EN pin is pulled low. If the EN pin is not pulled low for 64 ms, the power MOSFET switching PI-4098-082305 is normally disabled for 2.5 seconds. The auto-restart alternately enables and disables the switching of the power MOSFET until the fault condition is removed. Figure 5 illustrates auto-restart circuit operation in the presence of an output short circuit. Adaptive Switching Cycle On-Time Extension Adaptive switching cycle on-time extension keeps the cycle on until current limit is reached, instead of prematurely terminating after the DCMAX signal goes low. This feature reduces the minimum input voltage required to maintain regulation, extending hold-up time and minimizing the size of bulk capacitor required. The on-time extension is disabled during the startup of the power supply, until the power supply output reaches regulation. TinySwitch-LT Operation TinySwitch-LT devices operate in the current limit mode. When enabled, the oscillator turns the power MOSFET on at the beginning of each cycle. The MOSFET is turned off when the current ramps up to the current limit or when the DCMAX limit is reached. Since the highest current limit level and frequency of a TinySwitch-LT design are constant, the power delivered to the load is proportional to the primary inductance of the transformer and peak primary current squared. Hence, designing the supply involves calculating the primary inductance of the transformer for the maximum output power required. If the TinySwitch-LT is appropriately chosen for the power level, the current in the calculated inductance will ramp up to current limit before the DCMAX limit is reached. Enable Function TinySwitch-LT senses the EN pin to determine whether or not to proceed with the next switching cycle. The sequence of cycles is used to determine the current limit. Once a cycle is started, it always completes the cycle (even when the EN pin changes state half way through the cycle). This operation results in a power supply in which the output voltage ripple is determined by the output capacitor, amount of energy per switch cycle and the delay of the feedback. The EN pin signal is generated on the secondary by comparing the power supply output voltage with a reference voltage. The EN pin signal is high when the power supply output voltage is less than the reference voltage. In a typical implementation, the EN pin is driven by an optocoupler. The collector of the optocoupler transistor is connected to the EN pin and the emitter is connected to the SOURCE pin. The optocoupler LED is connected in series with a Zener diode across the DC output voltage to be regulated. When the output voltage exceeds the target regulation voltage level (optocoupler LED voltage drop plus Zener voltage), the optocoupler LED will start to conduct, pulling the EN pin low. The Zener diode can be replaced by a TL431 reference circuit 300 200 100 0 10 V V DRAIN 5 0 DC-OUTPUT 0 2500 5000 Time (ms) Figure 5. Auto-Restart Operation. 4 A 08/07 TNY174-180 for improved accuracy. ON/OFF Operation with Current Limit State Machine The internal clock of the TinySwitch-LT runs all the time. At the beginning of each clock cycle, it samples the EN pin to decide whether or not to implement a switch cycle, and based on the sequence of samples over multiple cycles, it determines the appropriate current limit. At high loads, the state machine sets the current limit to its highest value. At lighter loads, the state machine sets the current limit to reduced values. At near maximum load, TinySwitch-LT will conduct during nearly all of its clock cycles (Figure 6). At slightly lower load, it will "skip" additional cycles in order to maintain voltage regulation at the power supply output (Figure 7). At medium loads, cycles will be skipped and the current limit will be reduced (Figure 8). At very light loads, the current limit will be reduced even further (Figure 9). Only a small percentage of cycles will occur to satisfy the power consumption of the power supply. The response time of the ON/OFF control scheme is very fast compared to PWM control. This provides tight regulation and excellent transient response. Power Up/Down The TinySwitch-LT requires only a 0.1 F capacitor on the BYPASS/MULTI-FUNCTION pin to operate with standard current limit. Because of its small size, the time to charge this capacitor is kept to an absolute minimum, typically 0.6 ms. The time to charge will vary in proportion to the BYPASS/MULTIFUNCTION pin capacitor value when selecting different current limits. Due to the high bandwidth of the ON/OFF feedback, there is no overshoot at the power supply output. Figure 10 shows typical power up timing waveforms. Under startup and overload conditions, when the conduction time is less than 400 ns, the device reduces the switching frequency to maintain control of the peak drain current. During power down, the power MOSFET will switch for 64 ms after the output loses regulation. V EN CLOCK www..com D MAX I DRAIN V DRAIN PI-2749-050301 Figure 6. Operation at Near Maximum Loading. V EN CLOCK V EN CLOCK D MAX DC MAX I DRAIN I DRAIN V DRAIN V DRAIN PI-2667-090700 PI-2377-082305 Figure 7. Operation at Moderately Heavy Loading. Figure 8. Operation at Medium Loading. A 08/07 5 TNY174-180 PI-2381-1030801 200 V EN CLOCK 100 0 10 V DC-INPUT D MAX 5 0 V BYPASS I DRAIN 400 200 0 0 1 2 V DRAIN www..com Time (ms) V DRAIN Figure 10. Power Up. PI-2348-030801 PI-2661-072400 Figure 9. Operation at Very Light Load. 200 100 V DC-INPUT Figure 11 illustrates a typical power down timing waveform. No bias winding is needed to provide power to the chip because it draws the power directly from the DRAIN pin (see Functional Description above). This has two main benefits. First, for a nominal application, this eliminates the cost of a bias winding and associated components. Secondly, for battery charger applications, the current-voltage characteristic often allows the output voltage to fall close to zero volts while still delivering power. TinySwitch-LT accomplishes this without a forward bias winding and its many associated components. For applications that require very low no-load power consumption (50 mW), a resistor from a bias winding to the BYPASS/ MULTI-FUNCTION pin can provide the power to the chip. The minimum recommended current supplied is 1 mA. The BYPASS/MULTI-FUNCTION pin in this case will be clamped at 6.4 V. This method will eliminate the power draw from the DRAIN pin, thereby reducing the no-load power consumption and improving full-load efficiency. Current Limit Operation Each switching cycle is terminated when the DRAIN current reaches the current limit of the device. Current limit operation provides good line ripple rejection and relatively constant power delivery independent of input voltage. BYPASS/MULTI-FUNCTION Pin Capacitor The BYPASS/MULTI-FUNCTION pin can use a ceramic capacitor as small as 0.1 F for decoupling the internal power supply of the device. A larger capacitor size can be used to adjust the current limit. For TNY175-180, a 1 F BP/M pin capacitor will select a lower current limit equal to the standard current 0 400 300 200 100 0 0 .5 1 V DRAIN Time (s) Figure 11. Normal Power Down Timing. limit of the next smaller device and a 10 F BP/M pin capacitor will select a higher current limit equal to the standard current limit of the next larger device. The higher current limit level of the TNY180 is set to 850 mA typical. The TNY174 MOSFET does not have the capability for increased current limit so this feature is not available in this device. 6 A 08/07 TNY174-180 C5 2.2 nF 250 VAC VR1 P6KE150A D1 1N4007 J1 F1 3.15 A D2 1N4007 C1 6.8 F 400 V C2 22 F 400 V R1 1 k R2 100 C4 10 nF 1 kV D5 1N4007GP D3 1N4007 D4 1N4007 D7 BYV28-200 C10 1000 F 25 V L2 Ferrite Bead 3.5 x 7.6 mm NC T1 8 +12 V, 1 A J3 C11 100 F 25 V J4 RTN 1 6 3 85-265 VAC J2 RV1 275 VAC R7 4 20 2 5 D6 UF4003 L1 1 mH VR2 1N5255B 28 V R3 47 1/8 W R8* 21 k 1% EN BP/M C6 1 F 60 V VR3 BZX79-C11 11 V www..com *R5 is optional R6 390 1/8 W U2 PC817A C7 is configurable to adjust U1 current limit, see circuit description D S S TinySwitch-LT U1 TNY178P C7 100 nF 50 V R4 2 k 1/8 W PI-4773-073107 Figure 12. TNY178P, 12 V, 1 A Universal Input Power Supply. Applications Example The circuit shown in Figure 12 is a low cost, high efficiency, flyback power supply designed for 12 V, 1 A output from universal input using the TNY178. The supply features primary sensed output overvoltage latching shutdown protection, high efficiency (>80%), and very low noload consumption (<50 mW at 265 VAC). Output regulation is accomplished using a simple zener reference and optocoupler feedback. The rectified and filtered input voltage is applied to the primary winding of T1. The other side of the transformer primary is driven by the integrated MOSFET in U1. Diode D5, C2, R1, R2, and VR1 comprise the clamp circuit, limiting the leakage inductance turn-off voltage spike on the DRAIN pin to a safe value. The use of a combination a Zener clamp and parallel RC optimizes both EMI and energy efficiency. Resistor R2 allows the use of a slow recovery, low cost, rectifier diode by limiting the reverse current through D5. The selection of a slow diode also improves efficiency and conducted EMI but should be a glass passivated type, with a specified recovery time of 2 s. The output voltage is regulated by the Zener diode VR3. When the output voltage exceeds the sum of the Zener and optocoupler LED forward drop, current will flow in the optocoupler LED. This will cause the transistor of the optocoupler to sink current. When this current exceeds the ENABLE pin threshold current the next switching cycle is inhibited. When the output voltage falls below the feedback threshold, a conduction cycle is allowed to occur and, by adjusting the number of enabled cycles, output regulation is maintained. As the load reduces, the number of enabled cycles decreases, lowering the effective switching frequency and scaling switching losses with load. This provides almost constant efficiency down to very light loads, ideal for meeting energy efficiency requirements. As the TinySwitch-LT devices are completely self-powered, there is no requirement for an auxiliary or bias winding on the transformer. However by adding a bias winding, the output overvoltage protection feature can be configured, protecting the load against open feedback loop faults. When an overvoltage condition occurs, such that bias voltage exceeds the sum of VR2 and the BYPASS/MULTIFUNCTION (BP/M) pin voltage (28 V+5.85 V), current begins to flow into the BP/M pin. When this current exceeds ISD the internal latching shutdown circuit in TinySwitch-LT is activated. This condition is reset when the BP/M pin voltage drops below 2.6 V after removal of the AC input. In the example shown, on opening the loop, the OVP trips at an output of 17 V. A 08/07 7 TNY174-180 For lower no-load input power consumption, the bias winding may also be used to supply the TinySwitch-LT device. Resistor R8 feeds current into the BP/M pin, inhibiting the internal high voltage current source that normally maintains the BP/M pin capacitor voltage (C7) during the internal MOSFET off time. This reduces the no-load consumption of this design from 140 mW to 40 mW at 265 VAC. In addition to the simple input pi filter (C1, L1, C2) for differential mode EMI, this design makes use of E-ShieldTM shielding techniques in the transformer to reduce common mode EMI displacement currents, and R2 and C4 as a damping network to reduce high frequency transformer ringing. These techniques, combined with the frequency jitter of TNY178, give excellent conducted and radiated EMI performance with this design achieving >12 dBV of margin to EN55022 Class www..com B conducted EMI limits. For design flexibility the value of C7 can be selected to pick one of the 3 current limits options in U1. This allows the designer to select the current limit appropriate for the application. * Standard current limit (ILIMIT) is selected with a 0.1 F BP/M pin capacitor and is the normal choice for typical enclosed adapter applications. When a 1 F BP/M pin capacitor is used, the current limit is reduced (ILIMITred or ILIMIT-1) offering reduced RMS device currents and therefore improved efficiency, but at the expense of maximum power capability. This is ideal for thermally challenging designs where dissipation must be minimized. When a 10 F BP/M pin capacitor is used, the current limit is increased (ILIMITinc or ILIMIT+1), extending the power capability for applications requiring higher peak power or continuous power where the thermal conditions allow. 1. The minimum DC input voltage is 100 V or higher for 85 VAC input, or 220 V or higher for 230 VAC input or 115 VAC with a voltage doubler. The value of the input capacitance should be sized to meet these criteria for AC input designs. 2. Efficiency of 75%. 3. Minimum data sheet value of I2f. 4. Transformer primary inductance tolerance of 10%. 5. Reflected output voltage (VOR) of 135 V. 6. Voltage only output of 12 V with a fast PN rectifier diode. 7. Continuous conduction mode operation with transient KP* value of 0.25. 8. Increased current limit is selected for peak and open frame power columns and standard current limit for adapter columns. 9. The part is board mounted with SOURCE pins soldered to a sufficient area of copper and/or a heatsink is used to keep the SOURCE pin temperature at or below 110 C. 10. Ambient temperature of 50 C for open frame designs and 40 C for sealed adapters. *Below a value of 1, KP is the ratio of ripple to peak primary current. To prevent reduced power capability due to premature termination of switching cycles a transient KP limit of 0.25 is recommended. This prevents the initial current limit (IINIT) from being exceeded at MOSFET turn on. For reference, Table 2 provides the minimum practical power delivered from each family member at the three selectable current limit values. This assumes open frame operation (not thermally limited) and otherwise the same conditions as listed above. These numbers are useful to identify the correct current limit to select for a given device and output power requirement. Overvoltage Protection The output overvoltage protection provided by TinySwitch-LT uses an internal latch that is triggered by a threshold current of approximately 5.5 mA into the BP/M pin. In addition to an internal filter, the BP/M pin capacitor forms an external filter providing noise immunity from inadvertent triggering. For the bypass capacitor to be effective as a high frequency filter, the capacitor should be located as close as possible to the SOURCE and BP/M pins of the device. For best performance of the OVP function, it is recommended that a relatively high bias winding voltage is used, in the range of 15 V-30 V. This minimizes the error voltage on the bias winding due to leakage inductance and also ensures adequate voltage during no-load operation from which to supply the BP/M pin for reduced no-load consumption. Selecting the Zener diode voltage to be approximately 6 V above the bias winding voltage (28 V for 22 V bias winding) * * Further flexibility comes from the current limits between adjacent TinySwitch-LT family members being compatible. The reduced current limit of a given device is equal to the standard current limit of the next smaller device and the increased current limit is equal to the standard current limit of the next larger device. Key Application Considerations TinySwitch-LT Design Considerations Output Power Table The data sheet output power table (Table 1) represents the minimum practical continuous output power level that can be obtained under the following assumed conditions: 8 A 08/07 TNY174-180 OUTPUT POWER TABLE PRODUCT TNY174PN TNY175PN TNY176PN TNY177PN TNY178PN TNY179PN TNY180PN www..com 230 VAC 15% ILIMIT-1 9 10.8 11.8 15.1 19.4 23.7 28 ILIMIT 10.9 12 15.3 19.6 24 28.4 32.7 ILIMIT+1 9.1 15.1 19.4 23.7 28 32.2 36.6 ILIMIT-1 7.1 8.4 9.2 11.8 15.1 18.5 21.8 85-265 VAC ILIMIT 8.5 9.3 11.9 15.3 18.6 22 25.4 ILIMIT+1 7.1 11.8 15.1 18.5 21.8 25.2 28.5 Table 2. Minimum Practical Power at Three Selectable Current Limit Levels. gives good OVP performance for most designs, but can be adjusted to compensate for variations in leakage inductance. Adding additional filtering can be achieved by inserting a low value (10 to 47 ) resistor in series with the bias winding diode and/or the OVP Zener as shown by R7 and R3 in Figure 12. The resistor in series with the OVP Zener also limits the maximum current into the BP/M pin. Reducing No-load Consumption As TinySwitch-LT is self-powered from the BP/M pin capacitor, there is no need for an auxillary or bias winding to be provided on the transformer for this purpose. Typical no-load consumption when self-powered is <150 mW at 265 VAC input. The addition of a bias winding can reduce this down to <50 mW by supplying the TinySwitch-LT from the lower bias voltage and inhibiting the internal high voltage current source. To achieve this, select the value of the resistor (R8 in Figure 12) to provide the data sheet DRAIN supply current. In practice, due to the reduction of the bias voltage at low load, start with a value equal to 40% greater than the data sheet maximum current, and then increase the value of the resistor to give the lowest no-load consumption. Audible Noise The cycle skipping mode of operation used in TinySwitch-LT can generate audio frequency components in the transformer. To limit this audible noise generation the transformer should be designed such that the peak core flux density is below 3000 Gauss (300 mT). Following this guideline and using the standard transformer production technique of dip varnishing practically eliminates audible noise. Vacuum impregnation of the transformer should not be used due to the high primary capacitance and increased losses that result. Higher flux densities are possible, however careful evaluation of the audible noise performance should be made using production transformer samples before approving the design. Ceramic capacitors that use dielectrics such as Z5U, when used in clamp circuits, may also generate audio noise. If this is the case, try replacing them with a capacitor having a different dielectric or construction, for example a film type. TinySwitch-LT Layout Considerations Layout See Figure 13 for a recommended circuit board layout for TinySwitch-LT. Single Point Grounding Use a single point ground connection from the input filter capacitor to the area of copper connected to the SOURCE pins. Bypass Capacitor (CBP) The BP/M pin capacitor should be located as near as possible to the BP/M and SOURCE pins. EN Pin Keep traces connected to the EN pin short and, as far as is practical, away from all other traces and nodes above source potential including, but not limited to, the BYPASS and DRAIN pins. Primary Loop Area The area of the primary loop that connects the input filter capacitor, transformer primary and TinySwitch-LT together should be kept as small as possible. Primary Clamp Circuit A clamp is used to limit peak voltage on the DRAIN pin at turn off. This can be achieved by using an RCD clamp or a Zener (~200 V) and diode clamp across the primary winding. In all cases, to minimize EMI, care should be taken to minimize the circuit path from the clamp components to the transformer and TinySwitch-LT. A 08/07 9 TNY174-180 Maximize hatched copper areas ( ) for optimum heatsinking Output Rectifier Input Filter Capacitor PRI BIAS PRI T r a n s f o r m e r SEC Output Filter Capacitor Safety Spacing Y1Capacitor + HV - D S www..com TinySwitch-LT S BP/M BIAS S S TOP VIEW EN CBP Optocoupler DC + OUT PI-4779-073107 - Figure 13. Recommended Circuit Board Layout for TinySwitch-LT with Undervoltage Lock Out Resistor. Thermal Considerations The four SOURCE pins are internally connected to the IC lead frame and provide the main path to remove heat from the device. Therefore all the SOURCE pins should be connected to a copper area underneath the TinySwitch-LT to act not only as a single point ground, but also as a heatsink. As this area is connected to the quiet source node, this area should be maximized for good heatsinking. Similarly for axial output diodes, maximize the PCB area connected to the cathode. Y-Capacitor The placement of the Y-capacitor should be directly from the primary input filter capacitor positive terminal to the common/ return terminal of the transformer secondary. Such a placement will route high magnitude common mode surge currents away from the TinySwitch-LT device. Note - if an input (C, L, C) EMI filter is used then the inductor in the filter should be placed between the negative terminals of the input filter capacitors. Optocoupler Place the optocoupler physically close to the TinySwitch-LT to minimizing the primary-side trace lengths. Keep the high current, high voltage drain and clamp traces away from the optocoupler to prevent noise pick up. Output Diode For best performance, the area of the loop connecting the secondary winding, the output diode and the output filter capacitor, should be minimized. In addition, sufficient copper area should be provided at the anode and cathode terminals of the diode for heatsinking. A larger area is preferred at the quiet cathode terminal. A large anode area can increase high frequency radiated EMI. PC Board Leakage Currents TinySwitch-LT is designed to optimize energy efficiency across the power range and particularly in standby/no-load conditions. Current consumption has therefore been minimized to achieve this performance. The EN pin for example operates with very low threshold current levels and it is therefore recommended to limit parasitic currents into and out of the EN pin to levels below 1 A. Parasitic leakage currents into the EN pin are normally well below this 1A level when PC board assembly is in a well controlled production facility. However, high humidity conditions together with board and/or package contamination, either from no-clean flux or other contaminants, can reduce the surface resistivity enough to allow parasitic currents >1 A to flow into the EN pin. These currents can flow from higher voltage exposed solder pads close to the EN pin such as the BP/M pin solder pad. If the contamination levels in the PC board assembly facility are unknown, the application is open frame or operates in a high 10 A 08/07 TNY174-180 pollution degree environment, then an optional 390 k resistor should be added from EN pin to SOURCE pin to ensure that the parasitic leakage current into the EN pin is low. Note that typical values for surface insulation resistance (SIR) where no-clean flux has been applied according to the suppliers' guidelines are >>10 M and do not cause this issue. Quick Design Checklist As with any power supply design, all TinySwitch-LT designs should be verified on the bench to make sure that component specifications are not exceeded under worst case conditions. The following minimum set of tests is strongly recommended: 1. Maximum drain www..com voltage - Verify that the worst case VDS does not exceed 650 V at highest input voltage and peak (overload) output power. 2. Maximum drain current - At maximum ambient temperature, maximum input voltage and peak output (overload) power, verify drain current waveforms for any signs of transformer saturation and excessive leading edge current spikes at startup. Repeat under steady state conditions and verify that the leading edge current spike event is below ILIMIT(Min) at the end of the tLEB(Min). Under all conditions, the maximum drain current should be below the specified absolute maximum ratings. 3. Thermal Check - At specified maximum output power, minimum input voltage and maximum ambient temperature, verify that the temperature specifications are not exceeded for TinySwitch-LT, transformer, output diode, and output capacitors. Enough thermal margin should be allowed for part-to-part variation of the RDS(ON) of TinySwitch-LT as specified in the data sheet. Under low line, maximum power, a maximum TinySwitch-LT SOURCE pin temperature of 110 C is recommended to allow for these variations. A 08/07 11 TNY174-180 ABSOLUTE MAXIMUM RATINGS(1,5) DRAIN Voltage ................................................-0.3 V to 650 V DRAIN Peak Current: TNY174.......................400 (750) mA(2) TNY175.....................560 (1050) mA(2) TNY176.....................720 (1350) mA(2) TNY177.....................880 (1650) mA(2) TNY178...................1040 (1950) mA(2) TNY179.................. 1200 (2250) mA(2) TNY180.................. 1360 (2550) mA(2) EN Voltage .......................................................... -0.3 V to 9 V EN Current .................................................................. 100 mA BP/M Voltage .................................................. ....-0.3 V to 9 V Storage Temperature ......................................-65 C to 150 C Operating Junction Temperature(3) .................-40 C to 150 C www..com Lead Temperature(4) ....................................................... 260 C Notes: 1. All voltages referenced to SOURCE, TA = 25 C. 2. The higher peak DRAIN current is allowed while the DRAIN voltage is simultaneously less than 400 V. 3. Normally limited by internal circuitry. 4. 1/16 in. from case for 5 seconds. 5. Maximum ratings specified may be applied one at a time, without causing permanent damage to the product. Exposure to Absolute Maximum Rating conditions for extended periods of time may affect product reliability. THERMAL IMPEDANCE Notes: Thermal Impedance: P Package: 1. Measured on the SOURCE pin close to plastic interface. (JA) ........................... 70 C/W(2); 60 C/W(3) 2. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper clad. (JC)(1) ............................................... 11 C/W 3. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper clad. Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 C See Figure 14 (Unless Otherwise Specified) Min Typ Max Units CONTROL FUNCTIONS Output Frequency in Standard Mode Maximum Duty Cycle EN Pin Upper Turnoff Threshold Current EN Pin Voltage fOSC DCMAX TJ = 25 C See Figure 4 Average Peak-to-peak Jitter S1 Open 62 124 132 8 65 140 kHz % IDIS IEN = 25 A IEN = -25 A EN Current > IDIS (MOSFET Not Switching) See Note A TNY174PN TNY175PN IS2 EN Open (MOSFET Switching at fOSC) See Note B TNY176PN TNY177PN TNY178PN TNY179PN TNY180PN -150 1.8 0.8 -115 2.2 1.2 290 275 295 310 365 445 510 630 -90 2.6 1.6 A VEN IS1 V A 360 400 430 460 540 640 760 A DRAIN Supply Current 12 A 08/07 TNY174-180 Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 C See Figure 14 (Unless Otherwise Specified) Min Typ Max Units CONTROL FUNCTIONS (cont.) ICH1 VBP/M = 0 V, TJ = 25 C See Note C, D VBP/M = 4 V, TJ = 25 C See Note C, D TNY174 TNY175-179 TNY180 TNY174 TNY175-179 TNY180 -6 -8.3 -9.7 -4.1 -5 -6.6 5.6 0.80 IBP = 2 mA 6.0 -3.8 -5.4 -6.8 -2.3 -3.5 -4.6 5.85 0.95 6.4 -1.8 -2.5 -3.9 -1 -1.5 -2.1 6.15 1.20 6.7 V V V mA BP/M Pin Charge Current ICH2 www..com BP/M Pin Voltage VBP/M See Note C BP/M Pin Voltage VBP/MH Hysteresis BP/M Pin Shunt VSHUNT Voltage CIRCUIT PROTECTION di/dt = 50 mA/s TJ = 25 C See Note E di/dt = 55 mA/s TJ = 25 C See Note E di/dt = 70 mA/s TJ = 25 C See Note E ILIMIT di/dt = 90 mA/s TJ = 25 C See Note E di/dt = 110 mA/s TJ = 25 C See Note E di/dt = 130 mA/s TJ = 25 C See Note E di/dt = 150 mA/s TJ = 25 C See Note E TNY174PN 233 250 267 TNY175PN 256 275 294 TNY176PN 326 350 374 Standard Current Limit (BP/M Capacitor = 0.1 F) See Note D TNY177PN 419 450 481 mA TNY178PN 512 550 588 TNY179PN 605 650 695 TNY180PN 698 750 802 A 08/07 13 TNY174-180 Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 C See Figure 14 (Unless Otherwise Specified) di/dt = 50 mA/s TJ = 25 C See Note E di/dt = 55 mA/s TJ = 25 C See Note E di/dt = 70 mA/s TJ = 25 C See Notes E ILIMITred di/dt = 90 mA/s TJ = 25 C di/dt = 110 mA/s TJ = 25 C See Notes E di/dt = 130 mA/s TJ = 25 C See Notes E di/dt = 150 mA/s TJ = 25 C See Notes E di/dt = 50 mA/s TJ = 25 C See Notes E, F di/dt = 55 mA/s TJ = 25 C See Notes E di/dt = 70 mA/s TJ = 25 C See Notes E ILIMITinc di/dt = 90 mA/s TJ = 25 C See Notes E di/dt = 110 mA/s TJ = 25 C See Notes E di/dt = 130 mA/s TJ = 25 C See Notes E di/dt = 150 mA/s TJ = 25 C See Notes E Min Typ Max Units CIRCUIT PROTECTION (cont.) TNY174PN 196 210 233 TNY175PN 233 250 277 TNY176PN 256 275 305 www..com Reduced Current Limit (BP/M Capacitor = 1 F) See Note D TNY177PN 326 350 388 mA TNY178PN 419 450 499 TNY179PN 512 550 610 TNY180P 605 650 721 TNY174PN 196 210 233 TNY175PN 326 350 388 TNY176PN 419 450 499 Increased Current Limit (BP/M Capacitor = 10 F) See Note D TNY177PN 512 550 610 mA TNY178PN 605 650 721 TNY179PN 698 750 833 TNY180PN 791 850 943 14 A 08/07 TNY174-180 Conditions Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 C See Figure 14 (Unless Otherwise Specified) Min Typ Max Units CIRCUIT PROTECTION (cont.) Standard Current Limit, I2f = ILIMIT(TYP)2 TNY174-180PN x fOSC(TYP) 0.9 x I2f I2f 1.12 x I2f Power Coefficient If 2 Reduced Current Limit, I2f = ILIMITred(TYP)2 x fOSC(TYP) TNY174-180PN 0.9 x I2f I2f 1.16 x I2f A2Hz www..com 2 Increased Current Limit, I f = ILIMITinc(TYP)2 TNY174-180PN x fOSC(TYP) See Figure 19 TJ = 25 C, See Note G TJ = 25 C See Note G TJ = 25 C See Note G, H 0.9 x I2f 0.75 x ILIMIT(MIN) 170 I2f 1.16 x I2f mA Initial Current Limit Leading Edge Blanking Time Current Limit Delay Thermal Shutdown Temperature Thermal Shutdown Hysteresis BP/M Pin Shutdown Threshold Current BP/M Pin Power up Reset Threshold Voltage OUTPUT IINIT tLEB tILD 215 ns 150 ns TSD 135 142 150 C TSDH 75 C ISD 4 6.5 9 mA VBP/M(RESET) 1.6 2.6 3.6 V TNY174PN ID = 25 mA TJ = 25 C TJ = 100 C TJ = 25 C TJ = 100 C TJ = 25 C TJ = 100 C 28 42 19 29 14 21 32 48 22 33 16 24 ON-State Resistance RDS(ON) TNY175PN ID = 28 mA TNY176PN ID = 35 mA A 08/07 15 TNY174-180 Conditions Parameter OUTPUT (cont.) TNY177PN ID = 45 mA TNY178PN ID = 55 mA TNY179PN ID = 65 mA e Symbol SOURCE = 0 V; TJ = -40 to 125 C See Figure 14 (Unless Otherwise Specified) TJ = 25 C TJ = 100 C TJ = 25 C TJ = 100 C TJ = 25 C TJ = 100 C U . c Min Typ Max Units 7.8 11.7 5.2 7.8 3.9 5.8 2.6 3.9 9.0 13.5 6.0 9.0 4.5 6.7 3.0 4.5 50 100 200 A ON-State Resistance w w w . D a t a RDS(ON) S h TNY180PN ID = 75 mA e t 4 TJ = 25 C o m TJ = 100 C TNY174-176 TNY177-178 TNY179-180 VDS = 375 V, TJ = 50 C See Note G, I 650 OFF-State Drain Leakage Current IDSS1 VBP/M = 6.2 V VEN = 0 V VDS = 520 V TJ = 125 C See Note I VBP/M = 6.2 V VEN = 0 V IDSS2 15 Breakdown Voltage DRAIN Supply Voltage Auto-Restart ON-Time at fOSC Auto-Restart Duty Cycle BVDSS VBP = 6.2 V, VEN = 0 V, See Note J, TJ = 25 C V 50 TJ = 25 C See Note K TJ = 25 C V tAR DCAR 64 3 ms % 16 A 08/07 TNY174-180 NOTES: A. IS1 is an accurate estimate of device controller current consumption at no-load, since operating frequency is so low under these conditions. Total device consumption at no-load is the sum of IS1 and IDSS2. B Since the output MOSFET is switching, it is difficult to isolate the switching current from the supply current at the DRAIN. An alternative is to measure the BP/M pin current at 6.1 V. C. BP/M pin is not intended for sourcing supply current to external circuitry. D. To ensure correct current limit it is recommended that nominal 0.1 F / 1 F / 10 F capacitors are used. In addition, the BP/M capacitor value tolerance should be equal or better than indicated below across the ambient temperature range of the target application. The minimum and maximum capacitor values are guaranteed by characterization. Nominal BP/M Pin Cap Value 0.1 F 1 F 10 F Tolerance Relative to Nominal Capacitor Value Min -60% -50% -50% MAX +100% +100% NA www..com E. For current limit at other di/dt values, refer to Figure 21. F. TNY174 does not set an increased current limit value, but with a 10 F BP/M pin capacitor the current limit is the same as with a 1 F BP/M pin capacitor (reduced current limit value). G. This parameter is derived from characterization. H. This parameter is derived from the change in current limit measured at 1X and 4X of the di/dt shown in the ILIMIT specification. I. IDSS1 is the worst case OFF state leakage specification at 80% of BVDSS and maximum operating junction temperature. IDSS2 is a typical specification under worst case application conditions (rectified 265 VAC) for no-load consumption calculations. J. Breakdown voltage may be checked against minimum BVDSS specification by ramping the DRAIN pin voltage up to but not exceeding minimum BVDSS. K. Auto-restart on time has the same temperature characteristics as the oscillator (inversely proportional to frequency). A 08/07 17 TNY174-180 470 5W 470 S S S S BP/M EN D S2 S1 50 V 10 V 0.1 F NOTE: This test circuit is not applicable for current limit or output characteristic measurements. PI-4774-073107 www..com Figure 14. General Test Circuit. DCMAX (internal signal) tP EN tEN VDRAIN tP = 1 fOSC PI-4780-073107 Figure 15. Duty Cycle Measurement. Figure 16. Output Enable Timing. 0.8 Figure 17. Current Limit Envelope. 18 A 08/07 PI-4279-013006 TNY174-180 Typical Performance Characteristics PI-2213-012301 PI-4280-012306 1.1 1.2 1.0 0.8 0.6 0.4 0.2 0 Breakdown Voltage (Normalized to 25 C) 1.0 0.9 www..com -50 -25 Output Frequency (Normalized to 25 C) 0 25 50 75 100 125 150 -50 -25 0 25 50 75 100 125 Junction Temperature (C) Figure 18. Breakdown vs. Temperature. Junction Temperature (C) Figure 19. Frequency vs. Temperature. PI-4102-010906 Standard Current Limit (Normalized to 25 C) 1 0.8 0.6 0.4 0.2 0 -50 0 50 100 Normalized Current Limit 1.2 1.0 0.8 0.6 0.4 0.2 0 TNY174 TNY175 TNY176 TNY177 TNY178 TNY179 TNY180 Normalized di/dt = 1 50 mA/s 55 mA/s 70 mA/s 90 mA/s 110 mA/s 130 mA/s 150 mA/s Note: For the normalized current limit value, use the typical current limit specified for the appropriate BP/M capacitor. 150 1 2 3 4 Temperature (C) Figure 20. Standard Current Limit vs. Temperature. Normalized di/dt Figure 21. Current Limit vs. di/dt. PI-4083-082305 Drain Capacitance (pF) 250 Drain Current (mA) 200 150 100 50 0 0 Scaling Factors: TNY174 1.0 TNY175 1.5 TNY176 2.0 TNY177 3.5 TNY178 5.5 TNY179 7.3 TNY180 11 PI-4776-073107 300 1000 100 10 TCASE=25 C TCASE=100 C Scaling Factors: TNY174 1.0 TNY175 1.5 TNY176 2.0 TNY177 3.5 TNY178 5.5 TNY179 7.3 TNY180 11 1 2 4 6 8 10 0 100 200 300 400 500 600 DRAIN Voltage (V) Figure 22. Output Characteristic. Drain Voltage (V) Figure 23. COSS vs. Drain Voltage. A 08/07 PI-4775-073107 1.2 1.4 19 TNY174-180 Typical Performance Characteristics (cont.) Scaling Factors: TNY174 1.0 TNY175 1.5 TNY176 2.0 TNY177 3.5 TNY178 5.5 TNY179 7.3 TNY180 11 PI-4778-073107 50 40 Power (mW) 30 20 10 0 www..com 0 200 400 600 DRAIN Voltage (V) Figure 24. Drain Capacitance Power. 20 A 08/07 TNY174-180 PART ORDERING INFORMATION TinySwitch-LT Product Family Series Number Package Identifier P Plastic DIP-8C Pure Matte Tin (Pb-Free) Lead Finish TNY 178 P N N DIP-8C D S -Ewww..com .004 (.10) Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP) package with .300 inch row spacing. 2. Controlling dimensions are inches. Millimeter sizes are shown in parentheses. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. Pin locations start with Pin 1, and continue counter-clockwise to Pin 8 when viewed from the top. The notch and/or dimple are aids in locating Pin 1. Pin 3 is omitted. 5. Minimum metal to metal spacing at the package body for the omitted lead location is .137 inch (3.48 mm). 6. Lead width measured at package body. 7. Lead spacing measured with the leads constrained to be perpendicular to plane T. .240 (6.10) .260 (6.60) Pin 1 -D.367 (9.32) .387 (9.83) .057 (1.45) .068 (1.73) (NOTE 6) .125 (3.18) .145 (3.68) .015 (.38) MINIMUM -TSEATING PLANE .120 (3.05) .140 (3.56) .008 (.20) .015 (.38) .100 (2.54) BSC .014 (.36) .022 (.56) .048 (1.22) .053 (1.35) .137 (3.48) MINIMUM .300 (7.62) BSC (NOTE 7) .300 (7.62) .390 (9.91) P08C PI-3933-100504 T E D S .010 (.25) M A 08/07 21 TNY174-180 Revision Notes A Initial Release Date 08/07 For the latest updates, visit our website: www.powerint.com Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS. www..com PATENT INFORMATION The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A complete list of Power Integrations' patents may be found at www.powerint.com. Power Integrations grants its customers a license under certain patent rights as set forth at http://www.powerint.com/ip.htm. LIFE SUPPORT POLICY POWER INTEGRATIONS' PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein: 1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant injury or death to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. The PI logo, TOPSwitch, TinySwitch, LinkSwitch, DPA-Switch, PeakSwitch, Clampless, EcoSmart, E-Shield, Filterfuse, StackFET, PI Expert and PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies. (c)Copyright 2006, Power Integrations, Inc. Power Integrations Worldwide Sales Support Locations WORLD HEADQUARTERS 5245 Hellyer Avenue San Jose, CA 95138, USA. Main: +1-408-414-9200 Customer Service: Phone: +1-408-414-9665 Fax: +1-408-414-9765 e-mail: usasales@powerint.com CHINA (SHANGHAI) Rm 807-808A Pacheer Commercial Centre, 555 Nanjing Rd. West Shanghai, P.R.C. 200041 Phone: +86-21-6215-5548 Fax: +86-21-6215-2468 e-mail: chinasales@powerint.com CHINA (SHENZHEN) Rm 2206-2207, Block A, Electronics Science & Technology Bldg. 2070 Shennan Zhong Rd. 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